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PDF NCP1027 Data sheet ( Hoja de datos )
| Número de pieza | NCP1027 | |
| Descripción | High Voltage Switcher | |
| Fabricantes | ON Semiconductor | |
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NCP1027
High−Voltage Switcher
for Medium Power Offline
SMPS Featuring Low
Standby Power
The NCP1027 offers a new solution targeting output power levels
from a few watts up to 15 W in a universal mains flyback application.
Our proprietary high−voltage technology lets us include a power
MOSFET together with a startup current source, all directly
connected to the bulk capacitor. To prevent lethal runaway in low
input voltage conditions, an adjustable brown−out circuitry blocks
the activity until sufficient input level is reached.
Current−mode operation together with an adjustable ramp
compensation offers superior performance in universal mains
applications. Furthermore, an Over Power Protection pin brings the
ability to precisely compensate all internal delays in high input voltage
conditions and optimize the maximum output current capability.
Protection wise, a timer detects an overload or a short−circuit and
stops all operations, ensuring a safe auto−recovery, low duty cycle burst
operation. An integrated, auto−recovery, Overvoltage Protection
permanently monitors the VCC level and temporarily shuts down the
driving pulses in case of an unexpected feedback loop runaway.
Finally, a great RDS(on) figure makes the circuit an excellent choice
for standby/auxiliary offline power supplies or applications requiring
higher output power levels.
Features
• Built−in 700 V MOSFET with Typical RDS(on) of 5.8 W, TJ = 25°C
• Current−Mode Fixed Frequency Operation: 65 kHz and 100 kHz
• Fixed Peak Current of 800 mA
• Skip−Cycle Operation at Low Peak Currents
• Internal Current Source for Clean and Lossless Startup Sequence
• Auto−Recovery Output Short Circuit Protection with Timer−Based
Detection
• Auto−Recovery Overvoltage Protection with Auxiliary Winding
Operation
• Programmable Brown−Out Input for Low Input Voltage Detection
• Programmable Over Power Protection
• Input to Permanently Latchoff the Part
• Internal Frequency Jittering for Improved EMI Signature
• Extended Duty Cycle Operation to 80% Typical
• No−Load Input Standby Power of 85 mW @ 265 Vac
• 500 mW Loaded, Input Power of 715 mW @ 230 Vac
• These are Pb−Free Devices
Typical Applications
• Medium Power AC−DC Adapters for Chargers
• Auxiliary/Standby Power Supplies for ATX and TVS Power Supplies
Reference
230 VAC
90−265 VAC
NCP1027 − 5.8 W
25 W*
15 W*
*Typical values, open−frame, 65 kHz version, RqJA < 75°C/W, TA = 50°C.
http://onsemi.com
MARKING
DIAGRAM
8−LEAD PDIP
P SUFFIX
CASE 626A
P1027PXXX
AWL
YYWWG
XXX = 65 or 100
A = Assembly Location
WL = Wafer Lot
YY = Year
WW = Work Week
G = Pb−Free Package
PIN CONNECTIONS
VCC
Ramp Comp.
Brown−Out
FB
GND
OPP
(Top View)
Drain
ORDERING INFORMATION
Device
Package
Shipping*
NCP1027P065G
PDIP−8 50 Units / Rail
(Pb−Free)
NCP1027P100G
PDIP−8 50 Units / Rail
(Pb−Free)
*For additional information on our Pb−Free strategy
and soldering details, please download the
ON Semiconductor Soldering and Mounting
Techniques Reference Manual, SOLDERRM/D.
© Semiconductor Components Industries, LLC, 2006
December, 2006 − Rev. 3
1
Publication Order Number:
NCP1027/D
1 page  
NCP1027
ELECTRICAL CHARACTERISTICS (continued) (For typical values TJ = 25°C, for min/max values TJ = 0°C to +125°C,
Max TJ = 150°C, VCC = 8.0 V, unless otherwise noted.)
Characteristic
Pin Symbol Min Typ Max
CURRENT COMPARATOR
Maximum Internal Current Setpoint, Pin 4 Open, TJ = 25°C,
FSW = 65 kHz (Note 3)
Final Switch Current with a Primary Slope of 200 mA/ms,
FSW = 65 kHz (Note 4)
− Ipeak_27_CS_ 720
65 k
− Ipeak_27_SW_ −
65 k
800 880
820 −
Maximum Internal Current Setpoint, Pin 4 Open, TJ = 25°C,
FSW = 100 kHz (Note 3)
Final Switch Current with a Primary Slope of 200 mA/ms,
FSW = 100 kHz (Note 4)
Setpoint Decrease for a Pin 7 Injected Current of 40 mA, TJ = 25°C
Voltage Level in Pin 7 at which OPP Starts to Operate
− Ipeak_27_CS_ 720
100 k
− Ipeak_27_SW_ −
100 k
7 IOPP −
7 IOPPtripV −
800 880
820 −
23 −
1.5 −
Soft−Start Duration
Propagation Delay from Current Detection to Drain OFF State
Leading Edge Blanking Duration
INTERNAL OSCILLATOR
− TSS − 1.0 −
− Tprop − 100 −
− TLEB − 200 −
Oscillation Frequency (Note 5)
65 kHz Version, TJ = 25°C
− fOSC
58.5 65 71.5
Oscillation Frequency (Note 5)
100 kHz Version, TJ = 25°C
− fOSC
90 100 110
Frequency Jittering in Percentage of fOSC
Jittering Swing Frequency
−
fJitter
−
"6.0
−
− fswing − 300 −
Maximum Duty Cycle
−
Dmax
74 80 87
FEEDBACK SECTION
Internal Pullup Resistor
4 Rupp − 16 −
Ramp Compensation Level on Pin 1 – Rramp = 100 kW
2 Rlevel − 2.75 −
SKIP CYCLE GENERATION
Internal Skip Mode Level, in Percentage of Maximum Peak Current
− Iskip − 25 −
PROTECTIONS
Brown−Out Level
3
VBO
510 570 620
Brown−Out Hysteresis Current, TJ = 25°C (Note 3)
Brown−Out Hysteresis Current, TJ = 0°C to 125°C
Fault Validation further to Error Flag Assertion
3
IBOhyste
10 11.5 13
3 IBOhyste − 10 −
− TimerON 40 55 −
OFF Phase in Fault Mode
− TimerOFF − 440 −
Latching Voltage on Brown−Out Pin
3
Vlatch
3.15 3.5 3.85
Latch Input Integrating Filter Time Constant
3 TdelBOL − 20 −
OVP Integrating Filter Time Constant
− TdelOVP − 50 −
VCC Current at which the Switcher Stops Pulsing
TEMPERATURE MANAGEMENT
1
IOVP
6.0 8.5 11
Temperature Shutdown
−
TSD
160 −
−
Hysteresis in Shutdown
− − − 40 −
3. See characterization curves for full temperature span evolution.
4. The final switch current is: Ipeak_2X_CS + Tprop x Vin / Lp, with Vin the input voltage and Lp the primary inductor in a flyback.
5. Oscillator frequency is measured with disabled jittering.
Unit
mA
mA
mA
mA
%
V
ms
ns
ns
kHz
kHz
%
Hz
%
kW
V
%
mV
mA
mA
ms
ms
V
ms
ms
mA
°C
°C
http://onsemi.com
5
5 Page 
NCP1027
Startup Sequence
The NCP1027 includes a high−voltage startup circuitry,
directly deriving current from the bulk line to charge the
Vbulk
VCC capacitor. Figure 24 details the simplified internal
arrangement.
I1
RVCC
1
ICC1
+
IC1
←
5
I2 Iclamp
−+
+
CVCC
Vz = 8.7 V
VCCon
VCCoff
+
Iclamp > 6 mA
→ OVP fault
8
Figure 24. Internal Arrangement of the Startup Circuitry
When the power supply is first connected to the mains
outlet, the internal current source is biased and charges up
the VCC capacitor. When the voltage on this VCC capacitor
reaches the VCCON level (typically 8.5 V), the current
source turns off, reducing the amount of power being
dissipated. At this time, the VCC capacitor only supplies the
controller, and the auxiliary supply should take over before
VCC collapses below VCC(min). This VCC capacitor, CVCC,
must therefore be calculated to hold enough energy so that
VCC stays above VCC(min) (7.3 V typical) until the
auxiliary voltage fully takes over.
An auxiliary winding is needed to maintain the VCC in
order to self−supply the switcher. The VCC capacitor has
only a supply role and its value does not impact other
parameters such as fault duration or the frequency sweep
period for instance. As one can see in Figure 24, an internal
active Zener diode, protects the switcher against lethal VCC
runaways. This situation can occur if the feedback loop
optocoupler fails, for instance, and you would like to
protect the converter against an over voltage event. In that
case, the internal current increase incurred by the VCC
rapid growth triggers the over voltage protection (OVP)
circuit and immediately stops the output pulses for 440 ms.
Then a new startup attempt takes place to check whether
the fault has disappeared or not. The OVP paragraph gives
more design details on this particular section.
The VCC capacitor can be calculated knowing a) the
amount of energy that needs to be stored; b) the time it
takes for the auxiliary voltage to appear, and; c) the current
consumed by the controller at that time. For a better
understanding, Figure 25 shows how the voltage evolves
on the VCC capacitor upon startup.
http://onsemi.com
11
11 Page | ||
| Páginas | Total 30 Páginas | |
| PDF Descargar | [ Datasheet NCP1027.PDF ] | |
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